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power management 600khz step-up switching regulator with 2.2a, 45v switch typical application circuit SC2308A features input voltage range: 2.6v to 20v boost and sepic topologies up to 40v output in boost topology integrated 2.2a/45v switch 600khz constant switching frequency current-mode control eases compensation cycle-by-cycle current-limiting internal soft-start thermal shutdown protection low shutdown current (< a) 8-pin so lead-free package fully weee and rohs compliant applications telecommunication equipment point of load dc-dc converters portable devices ? ? ? ? ? ? ? ? ? ? ? ? ? ? ? description the SC2308A is a 600khz current-mode switching regulator with an integrated low-side 2.2a power transistor. the oper - ating supply voltage of the SC2308A ranges from that of a single li-ion cell to various pc board power supplies. the internal switch is rated at 45v, making the device suitable for high voltage boost and sepic applications. the SC2308A shuts down to less than a of supply current. the SC2308A uses peak current-mode pwm control for ease of loop compensation and excellent transient response. cycle-by-cycle current limiting lowers power transistor dissipation. an internal soft-start timer prevents output overshoot and limits the input current during start-up. thermal shutdown prevents the chip from overheating. rev. 2.0 c 1 : murata grm31cr61a475k c 2 ,c 3 : murata grm31cr61c226k l: coilcraft do3316p103 d 1 : on ss22 figure 1. 5v to 12v step-up converter e fficiency vs load c urrent v out = 12v 20 30 40 50 60 70 80 90 100 0 200 400 600 800 load current (ma) e fficiency (%) v in = 5v 4.7 f c 1 5v v in v out gnd en in sw fb on off ss22 d 1 c 2 22 f r 2 11.3k r 1 100k 12v, 0.8a l 10 h comp r 3 200k c 4 470pf SC2308A c 3 22 f
2 pin confguration marking information ordering information device package SC2308Astrt () (2) so-8 SC2308Aevb evaluation board notes: () available in tape and reel only. a reel contains 2,500 devices. (2) available in lead-free package only. device is weee and rohs compliant and halogen free. top view ja = 160 c/w 8-lead soic yyww - date code xxxxx - semtech lot number top view SC2308A SC2308A yyww xxxxx in fb gnd sw en 8 7 6 5 1 2 3 4 comp nc nc
3 exceeding the above specifcations may result in permanent damage to the device or device malfunction. operation outside of the parameters specifed in the electrical characteristics section is not recommended. absolute maximum ratings recommended operating conditions junction temperature range -40c to + 05c v in 2.6v to 20v thermal information ja , 8-lead soic (2) 60c/w maximum junction temperature + 50 c storage temperature range -65c to + 50c peak ir reflow temperature ( 0s to 30s) +260c unless otherwise noted: v in = v en = 3v, t j = -40 c to 05 c. typical values are at t j = 25 c. parameter symbol conditions min typ max units input supply maximum operating v in v in(max) 20 v v in start voltage v in rising 2.45 2.6 v shutdown supply current v en = 0 0.0 a quiescent supply current i q v fb = .5v (not switching) .3 .8 ma control loop feedback regulation voltage v ref .20 .22 .24 v v ref line regulation v in = 3v to 20v 0.002 0.005 %/v fb pin input bias current i fb fb in regulation -5 -25 na error amplifer transconductance g m v comp = . v, d i comp = 0.5a 47 w - error amplifer open-loop gain a v 5 db comp to switch current gain 4 a/v soft-start soft-start time (3) t ss 3 ms electrical characteristics in to gnd -0.3v to 24v sw -0.3v to 45v en -0.3v to v in + 0.3v fb -0.3v to v in + 0.3v comp -0.3v to v in + 0.3v esd protection level () 3.5kv notes: ( ) tested according to jedec standard jesd22-a 4-b. (2) calculated from package in still air, mounted to 3 x 4.5, 4 layer fr4 pcb with thermal vias under the exposed pad per jesd5 standards. notes: (3) time taken for the error amplifer soft-start input to rise from 0 to .22v. SC2308A
4 electrical characteristics (continued) SC2308A parameter symbol conditions min typ max units oscillator switching frequency f sw 500 630 750 khz minimum switch of-time t off(min) 60 ns minimum switch on-time t on(min) 200 ns minimum duty cycle d min 0 % maximum duty cycle d max 87 96 % power switch switch current limit (4) i lim 2.2 2.9 3.7 a switch saturation voltage v cesat i sw =2.2a 320 480 mv switch leakage current i lk v sw =2v 0. 0.5 a enable pin high voltage threshold v ih 2 v low voltage threshold v il 0.3 v enable pin current i en v en =0v 0.0 0. a v en =2v 3.3 5. v en =6v 3 25 over temperature protection thermal shutdown temperature t shdn t j rising 60 o c hysteresis t hyst 2 o c unless otherwise noted: v in = v en = 3v, t j = -40 c to 05 c. typical values are at t j = 25 c. notes: (4) switch current limit does not vary with duty cycle.
5 typical characteristics switch current limit vs temperature 2.0 2.2 2.4 2.6 2.8 3.0 -50 -25 0 25 50 75 100 125 temperature ( o c) current (a) v in = 3v error amplifier open-loop gain vs temperature 40 45 50 55 -50 -25 0 25 50 75 100 125 temperature ( o c) gain (db) v in = 3v error amplifier transconductance vs temperature 20 25 30 35 40 45 50 -50 -25 0 25 50 75 100 125 temperature ( o c) transconductance ( p : -1 ) v in = 3v feedback voltage vs temperature 1.20 1.21 1.22 1.23 -50 -25 0 25 50 75 100 125 temperature ( o c) voltage (v) v in = 3v efficiency vs load current v out = 5v 20 30 40 50 60 70 80 90 100 0 200 400 600 800 1000 1200 load current (ma) efficiency (%) v in = 3.3v e fficiency vs load c urrent v out = 12v 20 30 40 50 60 70 80 90 100 0 200 400 600 800 load current (ma) e fficiency (%) v in = 5v v in = 3.3v switc h saturation voltage vs switc h curre nt 0 100 200 300 400 500 0.0 0.5 1.0 1.5 2.0 2.5 3.0 3.5 s witch current (a) s aturation voltage (mv) v in = 3v 105 o c -45 o c 25 o c in pin curre nt v s switc h curre nt 0 20 40 60 80 0.0 0.5 1.0 1.5 2.0 2.5 3.0 3.5 s witch current (a) in p in current (ma) v in = 3v 25 o c SC2308A percentage frequency variation vs temperature -15 -10 -5 0 5 -50 -25 0 25 50 75 100 125 temperature ( o c) percenatge variation (%) v in = 3v
6 SC2308A en pin current vs v en 0 20 40 60 80 0 5 10 15 20 v en (v) current ( p a) -40 o c 25 o c 105 o c v in quiescent current vs temperature 0.0 0.5 1.0 1.5 2.0 -50 -25 0 25 50 75 100 125 temperature ( o c) current (ma) v en = 3v v in = 3v soft-start time (1) vs temperature 2.0 2.5 3.0 3.5 4.0 -50 -25 0 25 50 75 100 125 temperature ( o c) time (ms) v in = 3v typical characteristics (cont.) v in quiescent current vs v in 0.0 0.5 1.0 1.5 2.0 0 5 10 15 20 v in (v) current (ma) 25 o c 105 o c -40 o c minimum v in vs temperature 2.0 2.2 2.4 2.6 2.8 -50 -25 0 25 50 75 100 125 temperature ( o c) input voltage (v) notes: ( ) time taken for the error amplifer soft-start input to rise from 0 to .22v.
7 SC2308A pin descriptions pin # pin name pin function comp error amplifer output. the voltage at this pin controls the peak switch current. a series rc network from this pin to ground compensates the control loop. 2 fb the inverting input of the error amplifer. tie to an external resistive divider to set the output voltage. 3 en enable pin. pulling this pin below 0.3v shuts down the SC2308A to less than m a of quiescent current. applying more than 2v at this pin enables the SC2308A. for normal operation, this pin can be tied to in or driven from a logic gate with v oh > 2v. 4 gnd ground. tie to the ground plane. the converter output capacitor must be closely bypassed to the ground pin. 5 sw collector of the internal power transistor. connect to a boost inductor and a freewheeling diode. the maximum switching voltage spike at this pin should be limited to less than 45v. 6 in power supply pin. bypassed with capacitor close to the pin. 7 nc no connection. 8 nc no connection. block diagram figure 2. SC2308A block diagram ref not ready ea - fb 2 in 6 3 en shutdown thermal 1.22v + + r q s pwm - + + + - isen ilim + - 18mv s gnd 4 sw 5 600khz oscillator j q 1 start soft - + ss supply internal oc 6.3m ? comp 1 reference voltage t > 160 c clk slope comp
8 SC2308A general description and operation the SC2308A is a 600khz peak current-mode switching reg - ulator with an integrated 2.2a (minimum) low-side power transistor. the voltage reference runs off the input supply and is enabled by applying at least 2v at the en pin, as shown in the block diagram in figure 2. the reference also senses v in and produces a lockout signal ref not ready. this signal does not go low until there is enough v in head - room for the reference to achieve regulation (typically v in = 2.45v). the ref not ready signal and the temperature sensor control the internal regulator, which powers all of the internal control circuits. the error amplifier ea has two non-inverting inputs. the non-inverting input with the lower voltage predominates. one of the non-inverting inputs is biased to a precision .22v reference and the other non-inverting input is tied to a soft-start timer. before the internal regulator turns on, the output ss of the soft-start timer is discharged to ground. as the internal regulator turns on, it also releases the timer. the soft-start timer generates a slow rising ss ramp, which is fed into one of the non-inverting inputs of the ea. during power-up, the ss voltage becomes the ea effective non-inverting input voltage. in a boost converter, the part starts switching as v ss exceeds the fb voltage. if the soft-start ramp is sufficiently slow, then the fb voltage (hence the output voltage) will track v ss and there will be no output overshoot during start-up. it takes about 3ms to charge v ss from ground to the nominal feedback voltage. the end of charge v ss is significantly higher than .22v so that it has no effect on the error amplifier. soft-start also reduces the input start-up current. the clock clk resets the latch and blanks the power transis - tor q conduction. q is switched on at the trailing edge of the clock. the switch current is sensed with an integrated 6.3m w sense resistor. the sensed current summed with the slope-compensating ramp is fed into the modulating ramp input of the pwm comparator. the latch is set and q conduction is terminated when the modulating ramp intersects the error amplifier output. if the switch current exceeds 2.9a (the typical current limit), then the current- limit comparator ilim will set the latch and turn off q . due to separate pulse-width modulating and current limiting paths, cycle-by-cycle current limiting is not affected by slope compensation. the current-mode switching regulator is a dual-loop feed - back control system, designed to simplify loop compensa - tion. in the inner current loop, the ea output controls the peak inductor current. in the outer loop, the error amplifier regulates the output voltage. the double reactive poles of the output lc filter are reduced to a single real pole by the inner current loop, easing loop compensation. a simple, two-pole, single-zero compensator network con - nected from comp to ground is adequate to stabilize the converter.
9 applications information SC2308A duty cycle the duty cycle is the ratio of the switch on-time to the switching period. for a boost converter, the duty cycle in continuous-conduction mode (ccm) is: () where v cesat is the switch saturation voltage and v d is the rectifying diode forward voltage. setting the output voltage the converter output voltage is set with an external resis - tive divider. the center tap of the divider is tied to the fb pin ( figure 3). figure 3. r and r 2 divider sets v out the expression for v out is: (2) r can be calculated from the output voltage and r 2 as follows: (3) using large resistors for the fb voltage divider reduces power consumption. minimum of-time limitation there is also a 00ns minimum switch off-time, which limits the maximum duty cycle. this determines the maximum attainable output voltage for a given v in . using equation ( ), the maximum output voltage for a boost converter can be derived: (4) where d max is the maximum duty cycle. example: determine the highest output voltage that can be achieved from a 3v input using the SC2308A as a boost regulator. assuming v d = 0.5v, v cesat = 0.3v and using d max = 0.87: the transient headroom requirement further reduces the maximum achievable output voltage to less than 20v. maximum output current in a boost converter, the inductor is connected to the input. the inductor dc current is the regulator input current. when the power switch is turned on, the inductor current flows into the switch. when the power switch is off, the inductor current flows through the rectifying diode to the output. the output current is the average diode current. the diode current waveform is trapezoidal with a pulse width of ( Cd)t s (figure 4). the output current available from a boost converter, therefore, depends on the converter operating duty cycle. the power switch current in the SC2308A is internally limited to at least 2.2a. this is also the maximum peak inductor or the peak input current. if the inductor ripple current is low, then the maximum regulator input current will be very close to the switch current limit i lim . by estimating the conduction figure 4. current waveforms in a boost converter figure 4. current waveforms in a boost converter cesat d out in d out v v v v v v d v out r 2 r 1 fb 2 SC2308A ? ? 1 ? 2 1 out r r 1 220 . 1 v ? 1 ? ? 1 220 . 1 v r r out 2 1 d max cesat max in out v d 1 v d v v d v 6 . 20 5 . 0 87 . 0 1 3 . 0 87 . 0 3 v out u d switch current diode current on on off on on off on off (1 - d)t s dt s inductor current 0 0 i out i in switch current diode current on on off on on off on off (1 - d)t s dt s inductor current 0 0 i out i in
0 applications information (continued) SC2308A losses in both the switch and the diode, an expression for the maximum available output current of a boost converter can be derived using equation (5): (5) since switching losses are excluded in the derivation, the actual output current is over-estimated in equation (5). nevertheless, this calculation still provides a useful initial approximation. inductor selection the inductor must be able to handle the peak current i lim . first, the inductor should not saturate at i lim . second, the inductor needs to have low core loss at the switching fre - quency. inductors with ferrite cores are preferrable. more - over, the inductor should have low dcr for low copper loss. the inductance can be selected such that the inductor ripple current is between 20% to 40% of its average current for improved efficiency. the inductance can be calculated using equation (6): (6) the coilcraft do33 6p series and the sumida cdrh8d38np series inductors perform well in boost converters. the inductors selected must be suitable for a 750khz switch - ing frequency. input capacitor selection the input current in a boost converter is the inductor cur - rent, which is continuous with low rms current ripples. a 2.2 m f~4.7 m f ceramic capacitor is adequate for most applications. use x5r or better ceramic capacitors, since they have stable temperature and voltage coefficients. the voltage rating for the input capacitor should exceed the maximum input voltage by 0% to 25%. murata and tdk are two ceramic capacitor suppliers. output capacitor selection ceramic and low equivalent series resistance (esr) tantalum or polymer capacitors can be used for output filtering. in a buck converter, the inductor ripple current flows in the output capacitor, whereas in a boost converter, the output capacitor current is the difference between the rectifying diode current and the output current (figure 4). this cur - rent is discontinuous with high current amplitudes. for this reason, the output ripple voltage of a boost converter is always higher than that of a buck converter with the same inductor current and the same output capacitor. if tantalum or polymer capacitors are used at the converter output, then the converter output ripple voltage will be primarily determined by the capacitor esr, due to the rel - atively high esr of these capacitors. the output voltage ripple is the product of the peak inductor current and the output capacitor esr. for example, if two sanyo 6tpg 00m ( 00 m f, esr=70m w ) polymer capacitors are used for output filtering, then the output peak-to-peak ripple voltage will be 70mv, assuming a 2a peak inductor current. tantalum capacitor voltage derating is generally 50%. multi-layer ceramic capacitors, due to their extremely low esr (<5mf), are particularly well suited for output filtering. it is worth noting that the output ripple voltage resulting from charging and discharging of a 0f or a 22 m f ceramic capacitor is higher than the ripple voltage resulting from the capacitor esr. the output ripple voltage due to charging and discharging effects is calculated using the following equation: (7) x5r and x7r ceramic capacitors are the preferred types. rectifying diode for high efciency, schottky barrier diodes should be used as rectifying diodes for the SC2308A. these diodes should have an average forward current rating at least equal to the output current. the reverse blocking voltage of the schottky diode should be derated by 0%-20% for reliability. the schottky diode used in a 2v output step- up converter should have a reverse voltage rating of at least 5v (20% derating). ? ? o ? ? a in cesat d d out in lim ) max ( out v v v d v 45 d 1 v v i i sw l cesat in f i v v d l ? ' out sw out out c f di v ? '
in_en_out_il_3.3v to 5v@1.1a_en start in_en_out_il_5v to 12v@10ma_en start in_en_out_il_5v to 12v@800ma_en start SC2308A applications information (continued) ss22 and ss24 from on semiconductor and 0bq020 and 0bq040 from international rectifer are widely used schottky diodes. soft-start the SC2308A comprises an internal soft-start timer. the output (ss) of the soft-start timer (see figure 2), which forms the second non-inverting input of the feedback amplifier, is reset to zero before v in rises above its turn-on threshold. the ss voltage is subsequently charged from zero to the nominal feedback voltage ( .22v) in about 3ms. if a step-up converter is enabled by stepping the en input while connected to a live power supply, then its output voltage will rise linearly from approximately v in to its set voltage. the current drawn from the input power supply will be less than the switch current limit and there will be no output overshoot during start-up. figure 5 shows the start-up waveforms of the 5v to 2v step-up converter in figure and the 3.3v to 5v step-up converter in figure 0. notice that the regulator does not switch until the internal ss voltage exceeds the fb voltage. if the input power supply to a step-up converter is turned on with the en and the in pins shorted, then the start-up waveforms will depend on the input voltage ramp rate and the output load. the internal 3ms soft-start interval may be insufficient to keep the input start-up current below the switch current limit, especially with heavy loads and slow v in ramp. figure 6 shows the start-up waveforms of the step- up converters in figure and figure 0 when powering on using the agilent 6652a dc power supply. before v in rises above the input start voltage, there is no switching and the converter output simply follows v in . when starting into an 800ma constant-current load, the 5v to 2v converter reaches the cycle-by-cycle current limit and the output voltage ramp becomes non-linear {figure 6(c)}. there is, however, very little output voltage overshoot. boost converter start-up waveforms. en is stepped with input applied. (a) 5v to 2 v step-up regulator (figure ), i out = 0ma (b) 5v to 2 v step-up regulator, i out = 800ma (c) 3.3v to 5v step-up regulator (figure 0), i out = .a figure 5. v en 2v/div 2ms/div (b) 2ms/div v out 5v/div i l1 1a/ div v in 5v/div v en 2v/div v out 2v/div i l1 1a/ div v in 2v/div v en 2v/div 1ms/div (c) (a) v out 5v/div i l1 0.5a/ div v in 5v/div
2 SC2308A frequency compensation figure 7 shows the simplified equivalent model of a boost converter using the SC2308A. due to current-mode control, the double reactive poles attributed to the inductor are reduced to a single real pole. this pole results from the output capacitor and is at fre - quency: (8) where r l is the equivalent output load resistance and c out is the output capacitance. applications information (continued) figure . the simplifed model of a boost converter in_out_il_5v to 12v@10ma_in=en start in_out_il_5v to 12v@650ma_in=en start in_out_il_5v to 12v@800ma_in=en start in_out_il_3.3v to 5v@1.1a_in=en start boost converter start-up waveforms. en is tied to in and the regulator is powered on using the agilent 6652a power supply. (a) 5v to 12 v step-up regulator (figure 1), i out = 10ma (b) 5v to 12 v step-up regulator, i out = 650ma (c) 5v to 12 v step-up regulator, i out = 800ma (d) 3.3v to 5v step-up regulator (figure 10), i out = 1.1a figure 6. v out 5v/div i l1 1a/ div v in 5v/div 2ms/div 4ms/div v out 5v/div i l1 1a/ div v in 5v/div (a) (b) (d) (c) (d) out l 2 p c r 1 f s 1.22v gm - + r 3 c 4 comp fb c 6 power stage r 2 r 1 esr c out v in i out pwm modulator fi v ref v out r l v out 5v/div i l1 0.5a/ div v in 5v/div 2ms/div v out 5v/div i l1 1a/ div v in 5v/div 2ms/div
3 SC2308A applications information (continued) the power stage also has a right half plane (rhp) zero at: (9) the esr zero frequency is: (0) where r c is the esr of the output capacitor. r 3 and c 4 form a zero at: () with the assumption that c 4 >>c 6 , r 3 and c 6 also form a pole p 3 at frequency: (2) there is also a low-frequency integrator pole p formed by c 4 and the equivalent output resistance of the trans - conductance amplifier. the corresponding bode plots are shown in figure 8. bode magnitude plots of the power stage, the compensator, and the overall loop gain figure 8. the poles p , p 2 and the rhp zero z 2 all increase phase shift in the loop response. for stable operation, the overall loop gain should cross 0db with -20db/decade slope. due to the presence of the rhp zero, it is suggested that the 0db crossover frequency should not be more than 3 f 2 z . a simple two-pole, single-zero compensator network is adequate. the loop is compensated with r 3 , c 4 and c 6 from the comp pin to ground. the compensating zero z pro - vides phase boost beyond p 2 . in general, the converter will be more stable if the filter pole p 2 and the rhp zero z 2 are widely separated. the rhp zero moves to low frequency when either the duty cycle d or the output current i out increases. it is beneficial to use small inductors and larger output capacitors, especially when stepping up from low v in to high v out . an optional second pole can be placed at the power stage esr zero to attentuate any high-frequency noise. thermal shutdown thermal shutdown turns off the power switch and the control circuit as the junction temperature exceeds 60c. switching resumes when the junction temperature falls by 2c. l 2 r d 1 f l 2 2 z s out c 3 z c r 2 1 f s 4 3 1 z c r 2 1 f s 6 3 3 p c r 2 1 f s power - stage compensator loop gain f z1 f p3 f p2 f z2 f z3 f p3,4 f gain (db) crossover frequency, f c
4 SC2308A applications information (continued) board layout considerations in a boost converter, the main power switch, the rectifying diode, and the output filter capacitor carry pulse currents with high di/dt. for jitter-free operation, the size of the loop formed by these components should be minimized. the main power switch is integrated inside the SC2308A. therefore, the output capacitor should be connected close to the device ground pin. shortening the trace at the sw pin reduces the parasitic trace inductance. this decreases volt - age ringing at the sw node. the input capacitor should be placed close to the input and the gnd pins. figure 9 shows an example of external component placement around the SC2308A. l1 d1 r3 c4 gnd r2 v in v out jp c1 r1 sw c2 c3 c6 en u1 pin1 figure 9. suggested pcb layout for the SC2308A
5 4.7 m f c 1 12v v in v out gnd en in sw fb on off ss26 d 1 c 2 10 m f r 2 3.57k r 1 102k 36v, 0.4a l 22 m h comp r 3 487k c 4 220pf SC2308A c 6 10 m f c 5 10 m f c 3 10 m f SC2308A c 1 : murata grm31cr61a475k c 2 ,c 3 : sanyo 6tpg100m l: coilcraft do3316p103 d 1 : on ss22 typical application circuits c 1 : murata grm31cr61c475k c 2 ,c 3 ,c 5 ,c 6 : murata grm31cr61h106k l: cooper cd1-220 d 1 : on ss26 4.7 f c 1 3.3v v in v out gnd en in sw fb on off ss22 d 1 c 2 100 f r 2 59k r 1 180k 5v, 1.1a l 10 h comp r 3 200k c 4 220pf SC2308A c 3 100 f c 6 10pf figure 10. 3.3v to 5v step-up converter figure 11. 12v to 36v step-up converter
6 outline drawing soic-8 land pattern C soic-8 SC2308A see detail detail a a .050 bsc .236 bsc 8 .010 .150 .189 .154 .193 .012 - 8 0.25 1.27 bsc 6.00 bsc 3.90 4.90 - .157 .197 3.80 4.80 .020 0.31 4.00 5.00 0.51 bxn 2x n/2 tips seating aaa c e/2 2x 1 2 n a d a1 e1 bbb c a-b d ccc c e/2 a2 (.041) .004 .008 - .028 - - - - 0 .016 .007 .049 .004 .053 8 0 0.20 0.10 - 8 0.40 0.17 1.25 0.10 .041 .010 .069 .065 .010 1.35 (1.04) 0.72 - 1.04 0.25 - - - 1.75 1.65 0.25 0.25 - .010 .020 0.50 - c l (l1) 01 0.25 gage plane h h 3. dimensions "e1" and "d" do not include mold flash, protrusions or gate burrs. -b- controlling dimensions are in millimeters (angles in degrees). datums and to be determined at datum plane notes: 1. 2. -a- -h- side view a b c d e h plane reference jedec std ms-012, variation aa. 4. l1 n 01 bbb aaa ccc a b a2 a1 d e e1 l h e c dim min millimeters nom dimensions inches min max max nom e (.205) (5.20) z g y p (c) 3.00 .118 1.27 .050 0.60 .024 2.20 .087 7.40 .291 x inches dimensions z p y x dim c g millimeters this land pattern is for reference purposes only. consult your manufacturing group to ensure your company's manufacturing guidelines are met. notes: 1. reference ipc-sm-782a, rlp no. 300a. 2.
7 SC2308A semtech corporation power management products division 200 flynn road, camarillo, ca 930 2 phone: (805) 498-2 fax: (805) 498-3804 www.semtech.com contact information ? semtech 20 2 all rights reserved. reproduction in whole or in part is prohibited without the prior written consent of the copyright owner. the information presented in this document does not form part of any quotation or contract, is believed to be accurate and reliable and may be changed without notice. no liability will be accepted by the publisher for any conse - quence of its use. publication thereof does not convey nor imply any license under patent or other industrial or intellec - tual property rights. semtech assumes no responsibility or liability whatsoever for any failure or unexpected operation resulting from misuse, neglect improper installation, repair or improper handling or unusual physical or electrical stress including, but not limited to, exposure to parameters beyond the specified maximum ratings or operation outside the specified range. semtech products are not designed, intended, authorized or warranted to be suitable for use in life- support applications, devices or systems or other critical applications. inclusion of semtech prod - ucts in such applications is understood to be undertaken solely at the customers own risk. should a customer purchase or use semtech products for any such unauthorized application, the customer shall indemnify and hold semtech and its officers, employees, subsidiaries, affiliates, and distributors harmless against all claims, costs dam - ages and attorney fees which could arise. notice: all referenced brands, product names, service names and trademarks are the property of their respective owners.

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